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SEPTEMBER2018 VOLUME66 NUMBER9 IETMAB (ISSN0018-9480) THIS ISSUE INCLUDES THE JOURNAL WITHIN A JOURNAL ON MICROWAVE SYSTEMS AND APPLICATIONS MINI-SPECIAL ISSUE ON THE 2017 ASIA–PACIFIC MICROWAVE CONFERENCE Guest Editorial .......................................................................................................... A.-V. Pham 3911 MINI-SPECIALISSUEPAPERS Modified Shielding Effectiveness Equation for Novel Multilayered Waveguide-Below-Cutoff Array .................... ................................................................................... S. Kim, Y. Kim, S.-K. Pang, and J.-G. Yook 3912 Demonstration of Scattering Suppression by a Near-Zero-Index Metamaterial Composed of Dielectric Spheres ...... ......................................................................................................... Y. Takano and A. Sanada 3921 Analysis and Design of a 200-GHz SiGe-BiCMOS Loss-Compensated Distributed Power Divider ...................... ........................................................................................... P. V. Testa, C. Carta, and F. Ellinger 3927 An Ultra-Wideband Fast Frequency Ramp Synthesizer at 60 GHz With Low Noise Using a New Loop Gain Compensation Technique .......................................................... M. van Delden, N. Pohl, and T. Musch 3937 A Uniform Digital Predistorter for Concurrent Multiband Envelope Tracking RF Power Amplifiers With Different Envelopes ............................................................................... Q. Lu, F. Meng, N. Yang, and C. Yu 3947 Optimal Sizing of Two-Stage Cascaded Sparse Memory PolynomialModel for High Power Amplifiers Linearization ....................................................................... S. Wang, M. Abi Hussein, O. Venard, and G. Baudoin 3958 An Analytical Design Method for High-Speed VCSEL Driver With Optimized Energy Efficiency ...................... ..................................................................................... D. Schoeniger, R. Henker, and F. Ellinger 3966 REGULARPAPERSOFTHETRANSACTIONSONMICROWAVETHEORYANDTECHNIQUES EM Theory and Analysis Techniques Numerically Stable and Reliable Computation of Electromagnetic Modes in Multilayered Waveguides Using the Cauchy Integration Method With Automatic Differentiation .................... K. A. Michalski and M. M. Mustafa 3981 Devices and Modeling Low-Cost Ku-Band Waveguide Devices Using 3-D Printing and Liquid Metal Filling .................................... ...................................................................................... K. Y. Chan, R. Ramer, and R. Sorrentino 3993 Group Velocity and Backward-Wave Modes in Closed Anisotropic Waveguides ........ O. Demiryurek and N. Yener 4002 (Contents Continued on Page 3909) (Contents Continued from Front Cover) Modeling of Passive Intermodulation With Electrical Contacts in Coaxial Connectors .................................... ............................................................................ Q. Jin, J. Gao, G. T. Flowers, Y. Wu, and G. Xie 4007 Passive Circuits Design of a Class of Filtering Couplers With Reconfigurable Frequency .............................. F. Lin and H. Ma 4017 Compact Narrowband Filtering Rat-Race Coupler Using Quad-Mode Dielectric Resonator ............................... ............................................................................................. J.-X. Xu, X. Y. Zhang, and H.-Y. Li 4029 Design of Three-State Diplexer Using a Planar Triple-Mode Resonator ...................................................... ............................................ S.-W. Wong, B.-L. Zheng, J.-Y. Lin, Z.-C. Zhang, Y. Yang, L. Zhu, and Y. He 4040 CompactChebyshevDifferential-ModeBandpassFilteronλ/4CPSResonatorWithIntrinsicCommon-ModeRejection ................................................................................... L.-P. Feng, L. Zhu, S. Zhang, and X. Zhang 4047 Triple-Band Cavity Bandpass Filters ..................................................... L. Zhu, R. R. Mansour, and M. Yu 4057 Hybrid and Monolithic RF Integrated Circuits Highly Efficient Asymmetric Class-F−1/F GaN Doherty Amplifier .................................................. J. Kim 4070 A 5-GHz Low-Power Low-Noise Integer-N Digital Subsampling PLL With SAR ADC PD .............................. ....................................................................... M. Liu, R. Ma, S. Liu, Z. Ding, P. Zhang, and Z. Zhu 4078 LETTERS Comments on “Branch-Line Couplers Using Unequal Line Lengths” ..................... Q. He, L. Zhu, and Z. Dong 4088 Authors’ Reply to “Comments on ‘Branch-Line Couplers Using Unequal Line Lengths”’ ................................ ............................................................................... C. Toker, M. Saglam, M. Ozme, and N. Gunalp 4089 Corrections to “Linear Analysis of High-Frequency Field-Effect Transistors Using the CN-FDTD Method” .......... .................................................................................................................... B. Honarbakhsh 4090 JOURNAL WITHIN A JOURNAL ON MICROWAVE SYSTEMS AND APPLICATIONS JOURNALWITHINAJOURNALPAPERS Wireless Communication Systems √ A 7.52-dB Noise Figure 128.75–132.25-GHz Super-Regenerative Receiver With 0.615-fW/ Hz NEP by Coupled Oscillator Networks for Portable Imaging System in 65-nm CMOS ........... S. Ma, H. Yu, Q. J. Gu, and J. Ren 4095 63.5–65.5-GHzTransmit/ReceivePhased-ArrayCommunicationLinkWith 0.5–2Gb/sat100–800m and± 50°Scan Angles ............................................... B. Rupakula, A. Nafe, S. Zihir, Y. Wang, T.-W. Lin, and G. Rebeiz 4108 A SiGe Highly Integrated FMCW Transmitter Module With a 59.5–70.5-GHz Single Sweep Cover .................... ................................................................................................................ I. M. Milosavljevic´, D. P. Krcˇum, Ð. P. Glavonjic´, S. P. Jovanovic´, V. R. Mihajlovic´, D. M. Tasovac, and V. M. Milovanovic´ 4121 A 3.1–10.6-GHz 57-Bands CMOS Frequency Synthesizer for UWB-Based Cognitive Radios ........................... ..................................................................................................... N.-S. Kim and J. M. Rabaey 4134 A Reflection-Aware Unified Modeling and Linearization Approachfor Power Amplifier Under Mismatch and Mutual Coupling ...................................... S. K. Dhar, A. Abdelhafiz, M. Aziz, M. Helaoui, and F. M. Ghannouchi 4147 Wireless Power Transfer and RFID Systems Accurate Modeling of Coil Inductance for Near-Field Wireless Power Transfer ............................................ ......................................................................... S. R. Khan, S. K. Pavuluri, and M. P. Y. Desmulliez 4158 Design Approach for Efficient Wireless Power Transfer Systems During Lateral Misalignment ......................... ................................................................................. A. Barakat, K. Yoshitomi, and R. K. Pokharel 4170 Integrated Cooperative Ambient Power Harvester Collecting Ubiquitous Radio Frequency and Kinetic Energy ....... ......................................................................................... X. Gu, S. Hemour, L. Guo, and K. Wu 4178 Analysis and Design of Distributed Power Detectors ............................................. S. Qayyum and R. Negra 4191 Microwave Imaging and Radar Applications On Monostatic and Bistatic System Concepts for mm-Wave Radar MMICs ................................................ .......................................................... M. Hitzler, P. Grüner, L. Boehm, W. Mayer, and C. Waldschmidt 4204 An X-Band Frequency-Modulated Continuous-Wave Radar Sensor System With a Single-Antenna Interface for Ranging Applications .................................. H.-C. Chou, Y.-H. Kao, C.-C. Peng, Y.-J. Wang, and T.-S. Chu 4216 Microwave Sensors and Biomedical Applications Integrated 240-GHz Dielectric Sensor With dc Readout Circuit in a 130-nm SiGe BiCMOS Technology .............. ... D.Wang,K.Schmalz,M.H.Eissa,J.Borngräber,M.Kucharski,M.Elkhouly,M.Ko,H.J.Ng,andD.Kissinger 4232 (Contents Continued on Page 3910) (Contents Continued from Page 3909) High Ranging Accuracy and Wide Detection Range Interferometry Based on Frequency-Sweeping Technique With Vital Sign Sensing Function ........................................................ T.-H. Liu, M.-L. Hsu, and Z.-M. Tsai 4242 Development and In Vivo Performance Evaluation of 10–60-MHz Band Impulse-Radio-Based Transceiver for Deep Implantation Having 10 Mb/s .................................................................................................... ................................... J. Wang, K. Nomura, H. Narita, F. Ito, D. Anzai, J. Bergsland, and I. Balasingham 4252 Doppler Vital Signs Detection in the Presence of Large-Scale Random Body Movements ................................ ........................................... Q. Lv, L. Chen, K. An, J. Wang, H. Li, D. Ye, J. Huangfu, C. Li, and L. Ran 4261 A Transmission Line Model for the Evaluation of MRI RF-Induced Fields on Active Implantable Medical Devices ................................................................. J. Liu, J. Zheng, Q. Wang, W. Kainz, and J. Chen 4271 Microwave Photonics Fundamental/SubharmonicPhotonic Microwave I/Q Up-Converterfor Single Sideband and Vector Signal Generation ...................................................................... Y. Gao, A. Wen, W. Jiang, Y. Fan, Y. He, and D. Zhou 4282 Flexible New Opto-Microwave Design Approach for Radio-Over-Fiber Applications: A Case Study of Low-Cost 60-GHz VCSEL-Based IF-RoF Link .......................... C. Viana, Z. G. Tegegne, J.-L. Polleux, and C. Algani 4293 Phase Noise Measurement of RF Signals by Photonic Time Delay and Digital Phase Demodulation ................... ...................................................................................................... J. Shi, F. Zhang, and S. 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IEEETRANSACTIONSONMICROWAVETHEORYANDTECHNIQUES 1 Guest Editorial THE 2017 Asia–Pacific Microwave Conference Guest Editor, who worked with the Editor-in-Chief and one (APMC 2017) was held in Kuala Lumpur, Malaysia, Associate Editor responsible for the regular issues of this on November 13, 2017–November 16, 2017. The conference TRANSACTIONS.Thispolicyensuredthatallpaperspresented was sponsored by the IEEE Microwave Theory and in this Mini-Special Issue were evaluated, not only using the Techniques(MTT) Society, organizedby the Malaysian IEEE same process as regularissue papers, but also under the same AP/MTT/EMCJointChapter,andtechnicallyco-sponsoredby Editorial Review Board. the European Microwave Association and the IEEE Antennas I would like to thank the authors for submitting and and Propagation Society. Out of ∼537 papers submitted, refining their manuscripts and the reviewers for their time ∼360paperswere acceptedforpresentationinthe conference and effort to carefully review the papers. I would like to andpublicationinthe2017APMCproceedings.Thesepapers thank Prof. José Carlos Pedro, IEEE TRANSACTIONS ON have also been published online on the IEEE Xplore website. MICROWAVE THEORY AND TECHNIQUES Editor-in-Chief, The technical program involved 430 authors coming from and Prof. Kamran Ghorbani, Associate Editor, for their 40 different countries. guidance and support of this Mini-Special Issue. Finally, This Mini-Special Issue restarts the tradition of publishing I hope that future APMC and its authors will continue the extended papers of the APMC in this TRANSACTIONS. The tradition of publishing extended conference papers in this submissions, open to all authors of the papers presented, TRANSACTIONS. were due on January 15, 2018. A total of 20 papers were submitted. The submitted extended papers went through the same peer-review process as regular submissions to this TRANSACTIONS. After being carefully reviewed, seven ANH-VUPHAM, Guest Editor papers were accepted for publication. Departmentof Electrical and Computer Engineering The editorial process for this TRANSACTIONS’ University of California at Davis Mini-Special Issue was handled by Prof. Anh-Vu Pham, Davis, CA 95618 USA Anh-Vu Pham (SM’03) received the B.E.E. (with highest Hons.), M.S., and Ph.D. degrees in electrical engineering from the Georgia Institute of Technology, Atlanta, GA, USA, in 1995, 1997, and 1999, respectively. In 1997, he co-founded RF Solutions, a fabless semiconductor company providing power amplifiers and RFICs for WiFi applications. RF Solutions was acquired by Anadigics in 2003. In 2008, he co-founded and served as the CTO of Planarmag Inc., which was acquired by TE Connectivity in 2010. From 1999 to 2002, he was an Assistant Professor with Clemson University, Clemson, SC, USA. He joined the University of California at Davis, Davis, CA, USA, in 2002, as an Assistant Professor and became a Full Professor in 2008, where he is currently the Co-Director of the Davis Millimeter Wave Research Center. He has authored ∼180 peer-reviewed papers, several book chapters, and 2 books. He conducts research on microwave and millimeter-wave integrated circuit design, power amplifiers, electronic packag- ing,sensors,energyharvesting,andphased-arrayantennas.Hisresearchhasbeensupportedby DARPA, NSF, ONR, AFRL, and numerous companies. Dr. Pham was a recipient of the National Science Foundation Career Award in 2001 and the 2008 Outstanding Young Engineer Award from the IEEE Microwave Theory and Techniques Society (MTT-S). He served as the Chair of the IEEE MTT-S Technical Coordinate Committee on Microwave and Millimeter Packaging from 2003 to 2006, and the IEEE InternationalMicrowaveSymposiumTechnicalCommittee on Power Amplifiers and IntegratedDevices. He was a Microwave Distinguished Lecturer of the IEEE MTT-S from 2010 to 2012. He was the Co-Chair of the Technical Program Committee for the IEEE MTT-S International Microwave Symposium in San Francisco, CA, USA, in 2016, and is the Co-Chair of the Technical Program Committee for the IEEE Asia–Pacific Microwave Conference. _____________________ Digital ObjectIdentifier 10.1109/TMTT.2018.2856308 0018-9480©2018IEEE.Personaluseispermitted, butrepublication/redistribution requires IEEEpermission. Seehttp://www.ieee.org/publications_standards/publications/rights/index.html formoreinformation. This article has been accepted for inclusion in a future issue of this journal. Content is final as presented, with the exception of pagination. IEEETRANSACTIONSONMICROWAVETHEORYANDTECHNIQUES 1 Modified Shielding Effectiveness Equation for Novel Multilayered Waveguide-Below-Cutoff Array Sangin Kim , Student Member, IEEE, Yuna Kim , Student Member, IEEE, Seung-Ki Pang, and Jong-Gwan Yook , Senior Member, IEEE Abstract—Thispaperpresentsanairflowanalysisandashield- shielding effectiveness (SE) is used as a performance mea- ing effectiveness (SE) analysis for a multilayered waveguide- sure.Fortheoreticalanalysis,thefinite-differencetime-domain below-cutoff array (WBCA) used to prevent electromagnetic method and the multilevel fast multipole method are com- penetration. The performance of the conventional unit square monly used [9]–[16]. WBCA structures are often applied WBCAandthemultilayeredWBCAiscompared.Fortheairflow analysis, the simulations are performed at the entrance and exit for POEs, such as ventilation and water pipes, because of of the shielding structure when an airflow velocity of 1 m/s is their excellent SE. However, the intrinsic purpose of the injected at the inlet. The velocity loss and pressure difference ventilationandwaterpipesistoprovidea paththroughwhich of the multilayered WBCA are improved compared with the air or water flows [17]. With the addition of the shielding unit square WBCA. In terms of the shielding, the SE of the structures, the conventional WBCA could interfere with the multilayered WBCA is compensated by increasing the number ofoverlappinglayers.Furthermore,anewSEequationisderived flow and increase the loss of flow velocity and pressure by modifying that of the unit square WBCA. difference [18]–[20]. Because public facilities and factories must satisfy the recommended airflow standards, a shielding Index Terms—Electromagnetic pulse (EMP), flow velocity, multilayer, pressure difference, shielding effectiveness (SE), SE structure has to be modified appropriately [17]. Furthermore, equation, waveguide-below-cutoff array (WBCA). fabrication with the conventional honeycomb or rectangular cell-type structures is difficult to fabricate and maintain. Tomitigatethesedisadvantages,amultilayeredWBCAreduc- I. INTRODUCTION ing the interference of flow is proposed as a shielding struc- HIGH-ENERGYelectromagneticpulse(EMP)mighthave ture [21]. The multilayered WBCA can provide a smooth a profound effect on social infrastructure [1], [2], and airflow compared with the conventional structures owing to protection against this threat is necessary, because EMP can its structural characteristics. Furthermore, the multilayered neutralizemosthigh-endelectronicdevices.Thus,electromag- WBCA can be optimized to provide the appropriate SE level neticshieldingshouldbesystematicallydesignedforimportant by increasing the number of overlapping layers. facilities containing sensitive electronic devices for critical To use these multilayered WBCAs to design large facili- social services [3]. An electromagnetic wave can penetrate ties, the SE of the multilayered WBCA must be accurately into the structures and cause the malfunctions and failures predicted. Instead of using full-wave simulation tools [22], of electronic equipment with the sudden increase in the an analytic SE equation would be beneficial to practical currentfloworvoltage.Becausetheelectromagneticwavecan engineers. Therefore, the SE equation of the multilayered penetrate through the opening apertures, the facilities should WBCAfortheventilationwasderived[23].However,themul- have shielded the point of entries (POE), such as windows, tilayered WBCA is used not only for ventilation but also door openings, ventilation, as well as water pipes [4]. for the material-filled waveguide, i.e., water pipes. Thus, Variousstudiesanddetailedanalysesonshieldingstructures theSEequationforthegeneralcase isrequiredandshouldbe have been reported hitherto [5]–[8]. Typically, the shield- proven. ing structures, such as a unit square waveguide-below-cutoff This paper demonstrates the advantages of the pro- array (WBCA) or honeycomb structure, are used, and the posed shielding structure by analyzing the airflow and SE in Section II. Subsequently, Section III presents the results Manuscript received January 14, 2018; revised March 30, 2018 and of the modified SE equation for the multilayered WBCA May 10, 2018; accepted May 27, 2018. This work was supported by a grant from the Infrastructure and Transportation Technology Promotion and compares the results from the full-wave simulation and ResearchProgramthroughtheMinistryofLand,InfrastructureandTransport modified SE equation. In addition, the proposed SE equation of the Korean Government. This paper is an expanded version from the will be validated by comparison with the measured result. Asia–PacificMicrowaveConference,KualaLumpur,November13–16,2017. (Correspondingauthor:Jong-GwanYook.) S.Kim,Y.Kim,andJ.-G.YookarewiththeDepartmentofElectrical and II. PERFORMANCE ANALYSIS OF ElectronicEngineering,YonseiUniversity,Seoul30722,SouthKorea(e-mail: THEMULTILAYEREDWBCA [email protected]; [email protected]). S.-K. Pang is with the Department of Architecture, Kyungmin University, Before the multilayered WBCA performance is analyzed, Uijeongbu11618,SouthKorea(e-mail:[email protected]). the structural characteristics will be first explained. Further- Color versions of one or more of the figures in this paper are available more,thissectiondemonstratestheadvantagesoftheproposed onlineathttp://ieeexplore.ieee.org. Digital ObjectIdentifier 10.1109/TMTT.2018.2846273 structure comparedwith the conventionalunit square WBCA. 0018-9480©2018IEEE.Personaluseispermitted, butrepublication/redistribution requires IEEEpermission. Seehttp://www.ieee.org/publications_standards/publications/rights/index.html formoreinformation. This article has been accepted for inclusion in a future issue of this journal. Content is final as presented, with the exception of pagination. 2 IEEETRANSACTIONSONMICROWAVETHEORYANDTECHNIQUES Fig.1. (a)Isometricviewoftheconventional unitsquareWBCA.(b)Front view oftheunitrectangular WBCA. Fig.3. SimulationconditionsofairflowwithsquareWBCAandmultilayered WBCA. Fig. 2. (a) Isometric view of the proposed two-layered WBCA. (b) Front view ofthetwo-layered WBCA. A. Airflow Analysis of the Multilayered WBCA TheconventionalunitsquareWBCA isdesignedbyarrang- ing the unit square cells, as shown in Fig. 1. Fig. 1 shows the isometric view, as well as front view, of the unit square WBCA. Here, a represents the length of the unit square cell, and l represents the depth of the WBCA. The SE of the unit square WBCA will be improved as a becomes smaller Fig.4. ComparisonofflowvelocitybetweensquareWBCAandmultilayered and l becomes larger. However, the airflow will be disturbed WBCAfromtwotoeightlayers whendepthl isthesame. because of the increased friction. To overcome this problem, amultilayeredWBCA,asshowninFig.2,isproposed.Inthis the waveguide bulkhead. Although the maximum air velocity structure,verticallyandhorizontallyelongatedwaveguidesare increasesinaspecificposition,themeanairvelocityisreduced cascaded to provide characteristics similar to those of the owing to the back flow of air and the increased friction. conventional WBCA. It is possible to design an arbitrary Therefore, a decrease in velocity will occur. As shown in the numberofWBCAlayersbycascadingtwoorthogonalsections results,itisclearthatthevelocitydecreaseinthemultilayered for a given SE level. WBCA is smaller than that of the unit square WBCA. The An airflow analysis was performed for the unit square maximum air velocities at the entrance and exit are improved WBCA and the proposed multilayered WBCA. For compari- by 6% and 15%, respectively. son,the intakevelocityof theair atthe inletwas setto 1m/s, In addition, the pressure difference between the entrance as shown in Fig. 3, and the air velocity at the outlet was and the exit is calculated. As shown in Fig. 5, the unit square calculated.Thesimulationwas performedwith STAR-CCM+ WBCAshowsthelargestpressuredifferenceof0.8Pa,imply- 10.04 (win64) by CD-Adapco based on computational fluid ing an increased interference with the airflow. Meanwhile, dynamics [24]. The simulation was set to approximately the proposed WBCAs from two to eight layers show a rel- 2.7 million using a polyhedral volume mesh. The detailed atively small pressure difference between 0.46 and 0.66 Pa. geometrical parameters are shown in Fig. 3. Thus, the maximum pressure difference is improved by 33% Fig. 4 shows the average velocities of the airflow over the in the case of the two-layered WBCA. These results confirm surface at the entrance and exit planes of the unit square thattheairflowoftheproposedstructureissmootherthanthat WBCAandthemultilayeredWBCA.Theairflowisdividedby of the conventionalstructure. This article has been accepted for inclusion in a future issue of this journal. Content is final as presented, with the exception of pagination. KIMetal.: MODIFIEDSEEQUATIONFORNOVELMULTILAYEREDWBCA 3 Fig. 7. Comparison of pressure difference between square WBCA and Fig. 5. Comparison of pressure difference between square WBCA and multilayered WBCAfromtwotoeightlayers whenSEisthesame. multilayered WBCAfromtwotoeightlayers whendepthl isthesame. those of the unit square WBCA. This shows that the ratio TABLEI of the discontinuity area transmitting airflow is important. DEPTHlWITHTHENUMBEROFLAYERS Fig.7showsthepressuredifferencebetweentheentranceand theexit.ItalsoshowsthattheproposedWBCAsareimproved compared with the unit square WBCA. In conclusion, the airflow deteriorates as the number of layers and the depth of the multilayered WBCAs increase. However, when the same SE is required, the depths of the multilayered WBCA are drastically reduced to a log form, while the number of layers is increased by 2. In other words, asthe numberof layerincreases, the depthis reducedfurther; therefore, the results of airflow show more effectiveness than the conventional WBCA. B. SE Analysis of Multilayered WBCA To analyze the SE of the proposed multilayered WBCA, a plane wave is incident upon the WBCA entrance, and the transmissioncharacteristicsarecomparedwith theunitsquare WBCA. When the electromagnetic wave is incident from the outside, the TE or TE mode will have the lowest 10 01 attenuation among all the other modes generated, and the transmittedpowerof the unitsquareWBCA canbe expressed as shown [26] (cid:2) (cid:2) FWigB.C6A. CfroommptawriosotnooefigflhotwlavyeelrosciwtyhebnetSwEeeinssthqeuasraemWe.BCAandmultilayered P = 1Re (E(cid:2)×H(cid:2)∗)·ds(cid:2)= ωμ0a4|E10|2Re(β)e−2αl 10 2 4π2 (1) In the previous case, the airflow was analyzed when the depth l was the same. Next, the simulation of the WBCAs where E is the amplitude of the TE mode, α is the 10 10 having the same shielding effect is analyzed. Globally, attenuationconstant,β isthephaseconstant,μ istheintrinsic 0 the shielding effect of the facilities is specified to be 80 dB permeability, and ω is the angular frequency. It is clear that at 1 GHz [25].Therefore,when the side lengtha is the same, as a decreases or l becomes longer, the transmitted power the simulations are performed for the unit square WBCA will be decreased.For the unitsquareWBCA, the transmitted and the multilayered WBCA satisfying 80 dB. The depth 1 power is proportional to a4. Meanwhile, for the proposed of the WBCAs is set differently, and Table I shows the two-layered WBCA, the incident electromagnetic wave is depth l for the unit square WBCA and multilayered WBCA. transmitted through a vertical WBCA of depth l/2, and Fig. 6 shows the mean velocity at the entrance and exit then, the wave is transmitted through a horizontal WBCA of planes as in the previous case. In the two-layered WBCA, depth l/2. When the wave is traveling through the vertical the exit velocity is reduced more than that in the unit square WBCA section, the horizontalcomponentof the electric field WBCA, but the entrance velocity is not reduced more than experienceslessattenuation,becausethetangentialcomponent that in the unit square WBCA. From four to eight layers, of the electric field is reduced by the effective conductor. the entrance and exit velocities are improved compared with Meanwhile, the vertical component of the electric field is not This article has been accepted for inclusion in a future issue of this journal. Content is final as presented, with the exception of pagination. 4 IEEETRANSACTIONSONMICROWAVETHEORYANDTECHNIQUES Fig. 9. Results of electric field on the y–z cross section at 1 GHz. (a)2-layered WBCA.(b)8-layered WBCA.(c)16-layered WBCA. Fig.8. ComparisonofSEresultsbetweenunitsquareWBCAandmultilay- eredWBCAfrom2to64layers. effectively suppressed when it travels through the horizon- tal WBCA section. Hence, the two-layered WBCA provides insufficientattenuationcomparedwiththeunitsquareWBCA. This insufficient SE level can be compensated by increasing the number of cascading orthogonal sections. In this section, we show the SE calculation as a function Fig.10. Equivalent problemoftheair-filled WBCAandfielddefinitions. of the number of cascading sections of the multilayered WBCA.Thesimulationconditionsareidenticaltotheprevious case; the side length of the WBCA a is 10 mm, the depth used, such as by using the simulation tool or increasing of the WBCA l is 35 mm, the overall size of the WBCAs the simulation time as the number of layer increases. Thus, is 300 ×300 mm, and the structures were fabricated using the accurate mathematical formulas would be preferred. The copper as it is a good conductor. The multilayered WBCAs SEequationfortheunitsquareWBCAexists;however,noSE have been simulated from 2 to 64 layers with a 3-D full- equation is available for the multilayered WBCA. In this wave electromagnetic solver with the HFSS by ANSYS. The section, a modified SE equation for the multilayered WBCA WBCAsareusedinthesimulationproceededthroughtheideal will be derived. The SE is defined as the magnitude ratio of (cid:2) process, and the edges are perfectly sharp. To divide enough thetransmittedelectricfield(Et)andtheincidentelectricfield (cid:2) meshes to obtain the exact simulation results, the reference (Ei), as shown in the following: (cid:3)(cid:4) (cid:4)(cid:5) (cid:3)(cid:4) (cid:4)(cid:5) frequency was set to 2 GHz, and delta S (represents mesh (cid:4) (cid:2) (cid:4) (cid:4) (cid:2) (cid:4) (cid:4)P (cid:4) (cid:4)E (cid:4) stability) was set to 0.05. Subsequently, considering the peri- SE =10log (cid:4) i(cid:4) =20log (cid:4) i(cid:4) (2) (cid:4) (cid:2) (cid:4) (cid:4) (cid:2) (cid:4) odic structure,the periodicboundaryconditionwas used. The Pt Et SE results are obtained by comparison between port 1 and and the SE equation for the unit square WBCA is port 2, as shown in Fig. 3, when the signal was excited at expressed by (3), satisfying the boundary condition as shown port1. Fig. 8 showsthe SE curvesfor the unit squareWBCA in Fig. 10 [21], [27], [28] as well as for the multilayered vertical–horizontal WBCAs. (cid:4) (cid:4) Using only two layers, a 62-dB SE is obtained at 2 GHz; (cid:4)(η +η )2(cid:4) asthenumberoflayerincreases,theSElevelincreasedfurther. SE= R+ A =20log(cid:4)(cid:4) 04η η0 (cid:4)(cid:4) 0 0 (cid:6) (cid:7) Using eight layers, an SE level greater than 90 dB can be 2ka attainedat2GHz.Furthermore,Fig.9showstheelectricfield +20log(eαl)+20log (3) π insidethe multilayeredWBCAs onthe y–z crosssection.The results prove that as the number of layers increases, the elec- where η is the intrinsic impedance in air, k is the wavenum- 0 tric field is attenuated more during the transmission through ber, and R represents the shielding effect generated by the the intersection point. Additionally, as the number of layer reflectionloss, whereas A is theabsorptionloss. Additionally, increases, the SE level approaches that of the conventional thethirdtermof(3)representsthearrayeffect.Theattenuation square WBCA. constantα canbeexpressedasthefollowing(4)forametallic waveguide [27], [29]: III. MODIFIED SE EQUATION OF (cid:8) THEMULTILAYEREDWBCA √ (cid:6) f (cid:7)2 A. Derivation to the Modified SE Equation α =ω (cid:7)μ c −1 (4) f To predict the SE of the multilayered WBCA, a full- wave analysis that requires a high computation cost can be where f representsthe cutofffrequencyofa unitsquarecell. c This article has been accepted for inclusion in a future issue of this journal. Content is final as presented, with the exception of pagination. KIMetal.: MODIFIEDSEEQUATIONFORNOVELMULTILAYEREDWBCA 5 TABLEII CONSTANTCWITHTHENUMBEROFLAYERS Fig.11. SEresults withthenumberoflayers byfrequency. Fig.13. (a)Isometricviewoftheproposedtwo-layeredWBCAfillednonair material. (b)Frontview ofthetwo-layered WBCAfillednonairmaterial. The modified SE equation can be derived as shown in the following [23]: (cid:4) (cid:4) (cid:4)(η +η )2(cid:4) SE= R+ A =20log(cid:4)(cid:4) 0 0 (cid:4)(cid:4)+20log(eαleff) 4η η 0 0 (cid:6) (cid:7) Fig. 12. Mechanical equivalence of structure between square WBCA and 2ka two-layered WBCA. +20log . (5) π 2) Material-FilledWBCA: WhentheinsideoftheWBCAis filledwithanonairmaterialasshowninFig.13,theimpinging In practice, the SE equation changes with the material electromagneticwaveexperiencesimpedancediscontinuitiesat filled inside the waveguide. Therefore, in this paper, the SE thematerialinterfacesaswellasmultiplereflections,resulting equations are derived for the general cases. in multiple reflection loss. 1) Air-Filled WBCA: The SE equation of the multilayered Fig. 14 shows an equivalent problem for the material-filled WBCA can be derived from (3). From Fig. 11, it is clear WBCA problem. After applying the boundary conditions at that the SE level of the multilayered WBCA approaches that the two interfaces, the following simultaneous equations are of the square WBCA. Figs. 1(b) and 2(b) show that the obtained: shape of the unit square cells of the WBCAs appears the same when viewed from the front. As the cutoff frequency E +E = E +E (6) i r 1 2 value of the unit square cells is the same for both cases, E E E E i − r = 1 − 2 (7) the side length a of the multilayered WBCA is maintained in η η η η 0 0 the SE equation. Meanwhile, the depth l should be changed E e−γmleff + E eγmleff = E e−jβ0leff (8) effectively. Thus, by introducing the effective length (l ) as 1 2 t eff E E E shown in Fig. 12, the originalSE equation in (3) can be used 1e−γmleff − 2eγmleff = te−jβ0leff (9) η η η for the new multilayered WBCAs. It is noteworthy that l is 0 eff where η represents the impedance of the material-filled alwaysgreaterthanl to providethe same SE level.l can be definedasl =C×l, where C can be derivedfromeffthe full- waveguide and γm is the propagation constant with the eff material-filledwaveguide.Tosolvetheseequations,thereflec- wave simulation, as shown in Table II. First, the SE results tion and transmission coefficients are obtained by using the were obtainedbythe full-wavesimulation ofthe multilayered ratioof E /E and E /E . Thetransmissioncoefficientyields WBCAs withthesamedepth.Afterthoseweresubstitutedfor r i t i (3) to extractthe newl value, the constant value C is defined E 4η η (cid:9) (cid:6)η −η(cid:7)2 (cid:10)−1 as the ratio of the new l value and the physical depth. It is t = 0 1− 0 e−2αmleffe−j2βmleff e−αleff. E (η +η)2 η +η noteworthy that the constant value C convergesto one as the i 0 0 number of layers increases. (10)

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SEPTEMBER2018 VOLUME66 NUMBER9 IETMAB (ISSN0018-9480) THIS ISSUE INCLUDES THE JOURNAL WITHIN A JOURNAL ON MICROWAVE SYSTEMS AND APPLICATIONS MINI-SPECIAL ISSUE ON THE 2017 ASIA–PACIFIC MICROWAVE CONFERENCE Guest Editorial .......................................................................................................... A.-V. Pham 3911 MINI-SPECIALISSUEPAPERS Modified Shielding Effectiveness Equation for Novel Multilayered Waveguide-Below-Cutoff Array .................... ................................................................................... S. Kim, Y. Kim, S.-K. Pang, and J.-G. Yook 3912 Demonstration of Scattering Suppression by a Near-Zero-Index Metamaterial Composed of Dielectric Spheres ...... ......................................................................................................... Y. Takano and A. Sanada 3921 Analysis and Design of a 200-GHz SiGe-BiCMOS Loss-Compensated Distributed Power Divider ...................... ........................................................................................... P. V. Testa, C. Carta, and F. Ellinger 3927 An Ultra-Wideband Fast Frequency Ramp Synthesizer at 60 GHz With Low Noise Using a New Loop Gain Compensation Technique .......................................................... M. van Delden, N. Pohl, and T. Musch 3937 A Uniform Digital Predistorter for Concurrent Multiband Envelope Tracking RF Power Amplifiers With Different Envelopes ............................................................................... Q. Lu, F. Meng, N. Yang, and C. Yu 3947 Optimal Sizing of Two-Stage Cascaded Sparse Memory PolynomialModel for High Power Amplifiers Linearization ....................................................................... S. Wang, M. Abi Hussein, O. Venard, and G. Baudoin 3958 An Analytical Design Method for High-Speed VCSEL Driver With Optimized Energy Efficiency ...................... ..................................................................................... D. Schoeniger, R. Henker, and F. Ellinger 3966 REGULARPAPERSOFTHETRANSACTIONSONMICROWAVETHEORYANDTECHNIQUES EM Theory and Analysis Techniques Numerically Stable and Reliable Computation of Electromagnetic Modes in Multilayered Waveguides Using the Cauchy Integration Method With Automatic Differentiation .................... K. A. Michalski and M. M. Mustafa 3981 Devices and Modeling Low-Cost Ku-Band Waveguide Devices Using 3-D Printing and Liquid Metal Filling .................................... ...................................................................................... K. Y. Chan, R. Ramer, and R. Sorrentino 3993 Group Velocity and Backward-Wave Modes in Closed Anisotropic Waveguides ........ O. Demiryurek and N. Yener 4002 (Contents Continued on Page 3909) (Contents Continued from Front Cover) Modeling of Passive Intermodulation With Electrical Contacts in Coaxial Connectors .................................... ............................................................................ Q. Jin, J. Gao, G. T. Flowers, Y. Wu, and G. Xie 4007 Passive Circuits Design of a Class of Filtering Couplers With Reconfigurable Frequency .............................. F. Lin and H. Ma 4017 Compact Narrowband Filtering Rat-Race Coupler Using Quad-Mode Dielectric Resonator ............................... ............................................................................................. J.-X. Xu, X. Y. Zhang, and H.-Y. Li 4029 Design of Three-State Diplexer Using a Planar Triple-Mode Resonator ...................................................... ............................................ S.-W. Wong, B.-L. Zheng, J.-Y. Lin, Z.-C. Zhang, Y. Yang, L. Zhu, and Y. He 4040 CompactChebyshevDifferential-ModeBandpassFilteronλ/4CPSResonatorWithIntrinsicCommon-ModeRejection ................................................................................... L.-P. Feng, L. Zhu, S. Zhang, and X. Zhang 4047 Triple-Band Cavity Bandpass Filters ..................................................... L. Zhu, R. R. Mansour, and M. Yu 4057 Hybrid and Monolithic RF Integrated Circuits Highly Efficient Asymmetric Class-F−1/F GaN Doherty Amplifier .................................................. J. Kim 4070 A 5-GHz Low-Power Low-Noise Integer-N Digital Subsampling PLL With SAR ADC PD .............................. ....................................................................... M. Liu, R. Ma, S. Liu, Z. Ding, P. Zhang, and Z. Zhu 4078 LETTERS Comments on “Branch-Line Couplers Using Unequal Line Lengths” ..................... Q. He, L. Zhu, and Z. Dong 4088 Authors’ Reply to “Comments on ‘Branch-Line Couplers Using Unequal Line Lengths”’ ................................ ............................................................................... C. Toker, M. Saglam, M. Ozme, and N. Gunalp 4089 Corrections to “Linear Analysis of High-Frequency Field-Effect Transistors Using the CN-FDTD Method” .......... .................................................................................................................... B. Honarbakhsh 4090 JOURNAL WITHIN A JOURNAL ON MICROWAVE SYSTEMS AND APPLICATIONS JOURNALWITHINAJOURNALPAPERS Wireless Communication Systems √ A 7.52-dB Noise Figure 128.75–132.25-GHz Super-Regenerative Receiver With 0.615-fW/ Hz NEP by Coupled Oscillator Networks for Portable Imaging System in 65-nm CMOS ........... S. Ma, H. Yu, Q. J. Gu, and J. Ren 4095 63.5–65.5-GHzTransmit/ReceivePhased-ArrayCommunicationLinkWith 0.5–2Gb/sat100–800m and± 50°Scan Angles ............................................... B. Rupakula, A. Nafe, S. Zihir, Y. Wang, T.-W. Lin, and G. Rebeiz 4108 A SiGe Highly Integrated FMCW Transmitter Module With a 59.5–70.5-GHz Single Sweep Cover .................... ................................................................................................................ I. M. Milosavljevic´, D. P. Krcˇum, Ð. P. Glavonjic´, S. P. Jovanovic´, V. R. Mihajlovic´, D. M. Tasovac, and V. M. Milovanovic´ 4121 A 3.1–10.6-GHz 57-Bands CMOS Frequency Synthesizer for UWB-Based Cognitive Radios ........................... ..................................................................................................... N.-S. Kim and J. M. Rabaey 4134 A Reflection-Aware Unified Modeling and Linearization Approachfor Power Amplifier Under Mismatch and Mutual Coupling ...................................... S. K. Dhar, A. Abdelhafiz, M. Aziz, M. Helaoui, and F. M. Ghannouchi 4147 Wireless Power Transfer and RFID Systems Accurate Modeling of Coil Inductance for Near-Field Wireless Power Transfer ............................................ ......................................................................... S. R. Khan, S. K. Pavuluri, and M. P. Y. Desmulliez 4158 Design Approach for Efficient Wireless Power Transfer Systems During Lateral Misalignment ......................... ................................................................................. A. Barakat, K. Yoshitomi, and R. K. Pokharel 4170 Integrated Cooperative Ambient Power Harvester Collecting Ubiquitous Radio Frequency and Kinetic Energy ....... ......................................................................................... X. Gu, S. Hemour, L. Guo, and K. Wu 4178 Analysis and Design of Distributed Power Detectors ............................................. S. Qayyum and R. Negra 4191 Microwave Imaging and Radar Applications On Monostatic and Bistatic System Concepts for mm-Wave Radar MMICs ................................................ .......................................................... M. Hitzler, P. Grüner, L. Boehm, W. Mayer, and C. Waldschmidt 4204 An X-Band Frequency-Modulated Continuous-Wave Radar Sensor System With a Single-Antenna Interface for Ranging Applications .................................. H.-C. Chou, Y.-H. Kao, C.-C. Peng, Y.-J. Wang, and T.-S. Chu 4216 Microwave Sensors and Biomedical Applications Integrated 240-GHz Dielectric Sensor With dc Readout Circuit in a 130-nm SiGe BiCMOS Technology .............. ... D.Wang,K.Schmalz,M.H.Eissa,J.Borngräber,M.Kucharski,M.Elkhouly,M.Ko,H.J.Ng,andD.Kissinger 4232 (Contents Continued on Page 3910) (Contents Continued from Page 3909) High Ranging Accuracy and Wide Detection Range Interferometry Based on Frequency-Sweeping Technique With Vital Sign Sensing Function ........................................................ T.-H. Liu, M.-L. Hsu, and Z.-M. Tsai 4242 Development and In Vivo Performance Evaluation of 10–60-MHz Band Impulse-Radio-Based Transceiver for Deep Implantation Having 10 Mb/s .................................................................................................... ................................... J. Wang, K. Nomura, H. Narita, F. Ito, D. Anzai, J. Bergsland, and I. Balasingham 4252 Doppler Vital Signs Detection in the Presence of Large-Scale Random Body Movements ................................ ........................................... Q. Lv, L. Chen, K. An, J. Wang, H. Li, D. Ye, J. Huangfu, C. Li, and L. Ran 4261 A Transmission Line Model for the Evaluation of MRI RF-Induced Fields on Active Implantable Medical Devices ................................................................. J. Liu, J. Zheng, Q. Wang, W. Kainz, and J. Chen 4271 Microwave Photonics Fundamental/SubharmonicPhotonic Microwave I/Q Up-Converterfor Single Sideband and Vector Signal Generation ...................................................................... Y. Gao, A. Wen, W. Jiang, Y. Fan, Y. He, and D. Zhou 4282 Flexible New Opto-Microwave Design Approach for Radio-Over-Fiber Applications: A Case Study of Low-Cost 60-GHz VCSEL-Based IF-RoF Link .......................... C. Viana, Z. G. Tegegne, J.-L. Polleux, and C. Algani 4293 Phase Noise Measurement of RF Signals by Photonic Time Delay and Digital Phase Demodulation ................... ...................................................................................................... J. Shi, F. Zhang, and S. Pan 4306 IEEE MICROWAVETHEORYAND TECHNIQUES SOCIETY TheMicrowaveTheoryandTechniquesSocietyisanorganization,withintheframeworkoftheIEEE,ofmemberswithprincipalprofessionalinterestsinthefieldofmicrowave theoryandtechniques.AllmembersoftheIEEEareeligibleformembershipintheSocietyuponpaymentoftheannualSocietymembershipfeeof$24.00andobtainelectronic access, plus $50.00 per year for print media. For information on joining, write to the IEEE at the address below. Member copies of Transactions/Journals are for personal useonly. 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IEEETRANSACTIONSONMICROWAVETHEORYANDTECHNIQUES 1 Guest Editorial THE 2017 Asia–Pacific Microwave Conference Guest Editor, who worked with the Editor-in-Chief and one (APMC 2017) was held in Kuala Lumpur, Malaysia, Associate Editor responsible for the regular issues of this on November 13, 2017–November 16, 2017. The conference TRANSACTIONS.Thispolicyensuredthatallpaperspresented was sponsored by the IEEE Microwave Theory and in this Mini-Special Issue were evaluated, not only using the Techniques(MTT) Society, organizedby the Malaysian IEEE same process as regularissue papers, but also under the same AP/MTT/EMCJointChapter,andtechnicallyco-sponsoredby Editorial Review Board. the European Microwave Association and the IEEE Antennas I would like to thank the authors for submitting and and Propagation Society. Out of ∼537 papers submitted, refining their manuscripts and the reviewers for their time ∼360paperswere acceptedforpresentationinthe conference and effort to carefully review the papers. I would like to andpublicationinthe2017APMCproceedings.Thesepapers thank Prof. José Carlos Pedro, IEEE TRANSACTIONS ON have also been published online on the IEEE Xplore website. MICROWAVE THEORY AND TECHNIQUES Editor-in-Chief, The technical program involved 430 authors coming from and Prof. Kamran Ghorbani, Associate Editor, for their 40 different countries. guidance and support of this Mini-Special Issue. Finally, This Mini-Special Issue restarts the tradition of publishing I hope that future APMC and its authors will continue the extended papers of the APMC in this TRANSACTIONS. The tradition of publishing extended conference papers in this submissions, open to all authors of the papers presented, TRANSACTIONS. were due on January 15, 2018. A total of 20 papers were submitted. The submitted extended papers went through the same peer-review process as regular submissions to this TRANSACTIONS. After being carefully reviewed, seven ANH-VUPHAM, Guest Editor papers were accepted for publication. Departmentof Electrical and Computer Engineering The editorial process for this TRANSACTIONS’ University of California at Davis Mini-Special Issue was handled by Prof. Anh-Vu Pham, Davis, CA 95618 USA Anh-Vu Pham (SM’03) received the B.E.E. (with highest Hons.), M.S., and Ph.D. degrees in electrical engineering from the Georgia Institute of Technology, Atlanta, GA, USA, in 1995, 1997, and 1999, respectively. In 1997, he co-founded RF Solutions, a fabless semiconductor company providing power amplifiers and RFICs for WiFi applications. RF Solutions was acquired by Anadigics in 2003. In 2008, he co-founded and served as the CTO of Planarmag Inc., which was acquired by TE Connectivity in 2010. From 1999 to 2002, he was an Assistant Professor with Clemson University, Clemson, SC, USA. He joined the University of California at Davis, Davis, CA, USA, in 2002, as an Assistant Professor and became a Full Professor in 2008, where he is currently the Co-Director of the Davis Millimeter Wave Research Center. He has authored ∼180 peer-reviewed papers, several book chapters, and 2 books. He conducts research on microwave and millimeter-wave integrated circuit design, power amplifiers, electronic packag- ing,sensors,energyharvesting,andphased-arrayantennas.Hisresearchhasbeensupportedby DARPA, NSF, ONR, AFRL, and numerous companies. Dr. Pham was a recipient of the National Science Foundation Career Award in 2001 and the 2008 Outstanding Young Engineer Award from the IEEE Microwave Theory and Techniques Society (MTT-S). He served as the Chair of the IEEE MTT-S Technical Coordinate Committee on Microwave and Millimeter Packaging from 2003 to 2006, and the IEEE InternationalMicrowaveSymposiumTechnicalCommittee on Power Amplifiers and IntegratedDevices. He was a Microwave Distinguished Lecturer of the IEEE MTT-S from 2010 to 2012. He was the Co-Chair of the Technical Program Committee for the IEEE MTT-S International Microwave Symposium in San Francisco, CA, USA, in 2016, and is the Co-Chair of the Technical Program Committee for the IEEE Asia–Pacific Microwave Conference. _____________________ Digital ObjectIdentifier 10.1109/TMTT.2018.2856308 0018-9480©2018IEEE.Personaluseispermitted, butrepublication/redistribution requires IEEEpermission. Seehttp://www.ieee.org/publications_standards/publications/rights/index.html formoreinformation. This article has been accepted for inclusion in a future issue of this journal. Content is final as presented, with the exception of pagination. IEEETRANSACTIONSONMICROWAVETHEORYANDTECHNIQUES 1 Modified Shielding Effectiveness Equation for Novel Multilayered Waveguide-Below-Cutoff Array Sangin Kim , Student Member, IEEE, Yuna Kim , Student Member, IEEE, Seung-Ki Pang, and Jong-Gwan Yook , Senior Member, IEEE Abstract—Thispaperpresentsanairflowanalysisandashield- shielding effectiveness (SE) is used as a performance mea- ing effectiveness (SE) analysis for a multilayered waveguide- sure.Fortheoreticalanalysis,thefinite-differencetime-domain below-cutoff array (WBCA) used to prevent electromagnetic method and the multilevel fast multipole method are com- penetration. The performance of the conventional unit square monly used [9]–[16]. WBCA structures are often applied WBCAandthemultilayeredWBCAiscompared.Fortheairflow analysis, the simulations are performed at the entrance and exit for POEs, such as ventilation and water pipes, because of of the shielding structure when an airflow velocity of 1 m/s is their excellent SE. However, the intrinsic purpose of the injected at the inlet. The velocity loss and pressure difference ventilationandwaterpipesistoprovidea paththroughwhich of the multilayered WBCA are improved compared with the air or water flows [17]. With the addition of the shielding unit square WBCA. In terms of the shielding, the SE of the structures, the conventional WBCA could interfere with the multilayered WBCA is compensated by increasing the number ofoverlappinglayers.Furthermore,anewSEequationisderived flow and increase the loss of flow velocity and pressure by modifying that of the unit square WBCA. difference [18]–[20]. Because public facilities and factories must satisfy the recommended airflow standards, a shielding Index Terms—Electromagnetic pulse (EMP), flow velocity, multilayer, pressure difference, shielding effectiveness (SE), SE structure has to be modified appropriately [17]. Furthermore, equation, waveguide-below-cutoff array (WBCA). fabrication with the conventional honeycomb or rectangular cell-type structures is difficult to fabricate and maintain. Tomitigatethesedisadvantages,amultilayeredWBCAreduc- I. INTRODUCTION ing the interference of flow is proposed as a shielding struc- HIGH-ENERGYelectromagneticpulse(EMP)mighthave ture [21]. The multilayered WBCA can provide a smooth a profound effect on social infrastructure [1], [2], and airflow compared with the conventional structures owing to protection against this threat is necessary, because EMP can its structural characteristics. Furthermore, the multilayered neutralizemosthigh-endelectronicdevices.Thus,electromag- WBCA can be optimized to provide the appropriate SE level neticshieldingshouldbesystematicallydesignedforimportant by increasing the number of overlapping layers. facilities containing sensitive electronic devices for critical To use these multilayered WBCAs to design large facili- social services [3]. An electromagnetic wave can penetrate ties, the SE of the multilayered WBCA must be accurately into the structures and cause the malfunctions and failures predicted. Instead of using full-wave simulation tools [22], of electronic equipment with the sudden increase in the an analytic SE equation would be beneficial to practical currentfloworvoltage.Becausetheelectromagneticwavecan engineers. Therefore, the SE equation of the multilayered penetrate through the opening apertures, the facilities should WBCAfortheventilationwasderived[23].However,themul- have shielded the point of entries (POE), such as windows, tilayered WBCA is used not only for ventilation but also door openings, ventilation, as well as water pipes [4]. for the material-filled waveguide, i.e., water pipes. Thus, Variousstudiesanddetailedanalysesonshieldingstructures theSEequationforthegeneralcase isrequiredandshouldbe have been reported hitherto [5]–[8]. Typically, the shield- proven. ing structures, such as a unit square waveguide-below-cutoff This paper demonstrates the advantages of the pro- array (WBCA) or honeycomb structure, are used, and the posed shielding structure by analyzing the airflow and SE in Section II. Subsequently, Section III presents the results Manuscript received January 14, 2018; revised March 30, 2018 and of the modified SE equation for the multilayered WBCA May 10, 2018; accepted May 27, 2018. This work was supported by a grant from the Infrastructure and Transportation Technology Promotion and compares the results from the full-wave simulation and ResearchProgramthroughtheMinistryofLand,InfrastructureandTransport modified SE equation. In addition, the proposed SE equation of the Korean Government. This paper is an expanded version from the will be validated by comparison with the measured result. Asia–PacificMicrowaveConference,KualaLumpur,November13–16,2017. (Correspondingauthor:Jong-GwanYook.) S.Kim,Y.Kim,andJ.-G.YookarewiththeDepartmentofElectrical and II. PERFORMANCE ANALYSIS OF ElectronicEngineering,YonseiUniversity,Seoul30722,SouthKorea(e-mail: THEMULTILAYEREDWBCA [email protected]; [email protected]). S.-K. Pang is with the Department of Architecture, Kyungmin University, Before the multilayered WBCA performance is analyzed, Uijeongbu11618,SouthKorea(e-mail:[email protected]). the structural characteristics will be first explained. Further- Color versions of one or more of the figures in this paper are available more,thissectiondemonstratestheadvantagesoftheproposed onlineathttp://ieeexplore.ieee.org. Digital ObjectIdentifier 10.1109/TMTT.2018.2846273 structure comparedwith the conventionalunit square WBCA. 0018-9480©2018IEEE.Personaluseispermitted, butrepublication/redistribution requires IEEEpermission. Seehttp://www.ieee.org/publications_standards/publications/rights/index.html formoreinformation. This article has been accepted for inclusion in a future issue of this journal. Content is final as presented, with the exception of pagination. 2 IEEETRANSACTIONSONMICROWAVETHEORYANDTECHNIQUES Fig.1. (a)Isometricviewoftheconventional unitsquareWBCA.(b)Front view oftheunitrectangular WBCA. Fig.3. SimulationconditionsofairflowwithsquareWBCAandmultilayered WBCA. Fig. 2. (a) Isometric view of the proposed two-layered WBCA. (b) Front view ofthetwo-layered WBCA. A. Airflow Analysis of the Multilayered WBCA TheconventionalunitsquareWBCA isdesignedbyarrang- ing the unit square cells, as shown in Fig. 1. Fig. 1 shows the isometric view, as well as front view, of the unit square WBCA. Here, a represents the length of the unit square cell, and l represents the depth of the WBCA. The SE of the unit square WBCA will be improved as a becomes smaller Fig.4. ComparisonofflowvelocitybetweensquareWBCAandmultilayered and l becomes larger. However, the airflow will be disturbed WBCAfromtwotoeightlayers whendepthl isthesame. because of the increased friction. To overcome this problem, amultilayeredWBCA,asshowninFig.2,isproposed.Inthis the waveguide bulkhead. Although the maximum air velocity structure,verticallyandhorizontallyelongatedwaveguidesare increasesinaspecificposition,themeanairvelocityisreduced cascaded to provide characteristics similar to those of the owing to the back flow of air and the increased friction. conventional WBCA. It is possible to design an arbitrary Therefore, a decrease in velocity will occur. As shown in the numberofWBCAlayersbycascadingtwoorthogonalsections results,itisclearthatthevelocitydecreaseinthemultilayered for a given SE level. WBCA is smaller than that of the unit square WBCA. The An airflow analysis was performed for the unit square maximum air velocities at the entrance and exit are improved WBCA and the proposed multilayered WBCA. For compari- by 6% and 15%, respectively. son,the intakevelocityof theair atthe inletwas setto 1m/s, In addition, the pressure difference between the entrance as shown in Fig. 3, and the air velocity at the outlet was and the exit is calculated. As shown in Fig. 5, the unit square calculated.Thesimulationwas performedwith STAR-CCM+ WBCAshowsthelargestpressuredifferenceof0.8Pa,imply- 10.04 (win64) by CD-Adapco based on computational fluid ing an increased interference with the airflow. Meanwhile, dynamics [24]. The simulation was set to approximately the proposed WBCAs from two to eight layers show a rel- 2.7 million using a polyhedral volume mesh. The detailed atively small pressure difference between 0.46 and 0.66 Pa. geometrical parameters are shown in Fig. 3. Thus, the maximum pressure difference is improved by 33% Fig. 4 shows the average velocities of the airflow over the in the case of the two-layered WBCA. These results confirm surface at the entrance and exit planes of the unit square thattheairflowoftheproposedstructureissmootherthanthat WBCAandthemultilayeredWBCA.Theairflowisdividedby of the conventionalstructure. This article has been accepted for inclusion in a future issue of this journal. Content is final as presented, with the exception of pagination. KIMetal.: MODIFIEDSEEQUATIONFORNOVELMULTILAYEREDWBCA 3 Fig. 7. Comparison of pressure difference between square WBCA and Fig. 5. Comparison of pressure difference between square WBCA and multilayered WBCAfromtwotoeightlayers whenSEisthesame. multilayered WBCAfromtwotoeightlayers whendepthl isthesame. those of the unit square WBCA. This shows that the ratio TABLEI of the discontinuity area transmitting airflow is important. DEPTHlWITHTHENUMBEROFLAYERS Fig.7showsthepressuredifferencebetweentheentranceand theexit.ItalsoshowsthattheproposedWBCAsareimproved compared with the unit square WBCA. In conclusion, the airflow deteriorates as the number of layers and the depth of the multilayered WBCAs increase. However, when the same SE is required, the depths of the multilayered WBCA are drastically reduced to a log form, while the number of layers is increased by 2. In other words, asthe numberof layerincreases, the depthis reducedfurther; therefore, the results of airflow show more effectiveness than the conventional WBCA. B. SE Analysis of Multilayered WBCA To analyze the SE of the proposed multilayered WBCA, a plane wave is incident upon the WBCA entrance, and the transmissioncharacteristicsarecomparedwith theunitsquare WBCA. When the electromagnetic wave is incident from the outside, the TE or TE mode will have the lowest 10 01 attenuation among all the other modes generated, and the transmittedpowerof the unitsquareWBCA canbe expressed as shown [26] (cid:2) (cid:2) FWigB.C6A. CfroommptawriosotnooefigflhotwlavyeelrosciwtyhebnetSwEeeinssthqeuasraemWe.BCAandmultilayered P = 1Re (E(cid:2)×H(cid:2)∗)·ds(cid:2)= ωμ0a4|E10|2Re(β)e−2αl 10 2 4π2 (1) In the previous case, the airflow was analyzed when the depth l was the same. Next, the simulation of the WBCAs where E is the amplitude of the TE mode, α is the 10 10 having the same shielding effect is analyzed. Globally, attenuationconstant,β isthephaseconstant,μ istheintrinsic 0 the shielding effect of the facilities is specified to be 80 dB permeability, and ω is the angular frequency. It is clear that at 1 GHz [25].Therefore,when the side lengtha is the same, as a decreases or l becomes longer, the transmitted power the simulations are performed for the unit square WBCA will be decreased.For the unitsquareWBCA, the transmitted and the multilayered WBCA satisfying 80 dB. The depth 1 power is proportional to a4. Meanwhile, for the proposed of the WBCAs is set differently, and Table I shows the two-layered WBCA, the incident electromagnetic wave is depth l for the unit square WBCA and multilayered WBCA. transmitted through a vertical WBCA of depth l/2, and Fig. 6 shows the mean velocity at the entrance and exit then, the wave is transmitted through a horizontal WBCA of planes as in the previous case. In the two-layered WBCA, depth l/2. When the wave is traveling through the vertical the exit velocity is reduced more than that in the unit square WBCA section, the horizontalcomponentof the electric field WBCA, but the entrance velocity is not reduced more than experienceslessattenuation,becausethetangentialcomponent that in the unit square WBCA. From four to eight layers, of the electric field is reduced by the effective conductor. the entrance and exit velocities are improved compared with Meanwhile, the vertical component of the electric field is not This article has been accepted for inclusion in a future issue of this journal. Content is final as presented, with the exception of pagination. 4 IEEETRANSACTIONSONMICROWAVETHEORYANDTECHNIQUES Fig. 9. Results of electric field on the y–z cross section at 1 GHz. (a)2-layered WBCA.(b)8-layered WBCA.(c)16-layered WBCA. Fig.8. ComparisonofSEresultsbetweenunitsquareWBCAandmultilay- eredWBCAfrom2to64layers. effectively suppressed when it travels through the horizon- tal WBCA section. Hence, the two-layered WBCA provides insufficientattenuationcomparedwiththeunitsquareWBCA. This insufficient SE level can be compensated by increasing the number of cascading orthogonal sections. In this section, we show the SE calculation as a function Fig.10. Equivalent problemoftheair-filled WBCAandfielddefinitions. of the number of cascading sections of the multilayered WBCA.Thesimulationconditionsareidenticaltotheprevious case; the side length of the WBCA a is 10 mm, the depth used, such as by using the simulation tool or increasing of the WBCA l is 35 mm, the overall size of the WBCAs the simulation time as the number of layer increases. Thus, is 300 ×300 mm, and the structures were fabricated using the accurate mathematical formulas would be preferred. The copper as it is a good conductor. The multilayered WBCAs SEequationfortheunitsquareWBCAexists;however,noSE have been simulated from 2 to 64 layers with a 3-D full- equation is available for the multilayered WBCA. In this wave electromagnetic solver with the HFSS by ANSYS. The section, a modified SE equation for the multilayered WBCA WBCAsareusedinthesimulationproceededthroughtheideal will be derived. The SE is defined as the magnitude ratio of (cid:2) process, and the edges are perfectly sharp. To divide enough thetransmittedelectricfield(Et)andtheincidentelectricfield (cid:2) meshes to obtain the exact simulation results, the reference (Ei), as shown in the following: (cid:3)(cid:4) (cid:4)(cid:5) (cid:3)(cid:4) (cid:4)(cid:5) frequency was set to 2 GHz, and delta S (represents mesh (cid:4) (cid:2) (cid:4) (cid:4) (cid:2) (cid:4) (cid:4)P (cid:4) (cid:4)E (cid:4) stability) was set to 0.05. Subsequently, considering the peri- SE =10log (cid:4) i(cid:4) =20log (cid:4) i(cid:4) (2) (cid:4) (cid:2) (cid:4) (cid:4) (cid:2) (cid:4) odic structure,the periodicboundaryconditionwas used. The Pt Et SE results are obtained by comparison between port 1 and and the SE equation for the unit square WBCA is port 2, as shown in Fig. 3, when the signal was excited at expressed by (3), satisfying the boundary condition as shown port1. Fig. 8 showsthe SE curvesfor the unit squareWBCA in Fig. 10 [21], [27], [28] as well as for the multilayered vertical–horizontal WBCAs. (cid:4) (cid:4) Using only two layers, a 62-dB SE is obtained at 2 GHz; (cid:4)(η +η )2(cid:4) asthenumberoflayerincreases,theSElevelincreasedfurther. SE= R+ A =20log(cid:4)(cid:4) 04η η0 (cid:4)(cid:4) 0 0 (cid:6) (cid:7) Using eight layers, an SE level greater than 90 dB can be 2ka attainedat2GHz.Furthermore,Fig.9showstheelectricfield +20log(eαl)+20log (3) π insidethe multilayeredWBCAs onthe y–z crosssection.The results prove that as the number of layers increases, the elec- where η is the intrinsic impedance in air, k is the wavenum- 0 tric field is attenuated more during the transmission through ber, and R represents the shielding effect generated by the the intersection point. Additionally, as the number of layer reflectionloss, whereas A is theabsorptionloss. Additionally, increases, the SE level approaches that of the conventional thethirdtermof(3)representsthearrayeffect.Theattenuation square WBCA. constantα canbeexpressedasthefollowing(4)forametallic waveguide [27], [29]: III. MODIFIED SE EQUATION OF (cid:8) THEMULTILAYEREDWBCA √ (cid:6) f (cid:7)2 A. Derivation to the Modified SE Equation α =ω (cid:7)μ c −1 (4) f To predict the SE of the multilayered WBCA, a full- wave analysis that requires a high computation cost can be where f representsthe cutofffrequencyofa unitsquarecell. c This article has been accepted for inclusion in a future issue of this journal. Content is final as presented, with the exception of pagination. KIMetal.: MODIFIEDSEEQUATIONFORNOVELMULTILAYEREDWBCA 5 TABLEII CONSTANTCWITHTHENUMBEROFLAYERS Fig.11. SEresults withthenumberoflayers byfrequency. Fig.13. (a)Isometricviewoftheproposedtwo-layeredWBCAfillednonair material. (b)Frontview ofthetwo-layered WBCAfillednonairmaterial. The modified SE equation can be derived as shown in the following [23]: (cid:4) (cid:4) (cid:4)(η +η )2(cid:4) SE= R+ A =20log(cid:4)(cid:4) 0 0 (cid:4)(cid:4)+20log(eαleff) 4η η 0 0 (cid:6) (cid:7) Fig. 12. Mechanical equivalence of structure between square WBCA and 2ka two-layered WBCA. +20log . (5) π 2) Material-FilledWBCA: WhentheinsideoftheWBCAis filledwithanonairmaterialasshowninFig.13,theimpinging In practice, the SE equation changes with the material electromagneticwaveexperiencesimpedancediscontinuitiesat filled inside the waveguide. Therefore, in this paper, the SE thematerialinterfacesaswellasmultiplereflections,resulting equations are derived for the general cases. in multiple reflection loss. 1) Air-Filled WBCA: The SE equation of the multilayered Fig. 14 shows an equivalent problem for the material-filled WBCA can be derived from (3). From Fig. 11, it is clear WBCA problem. After applying the boundary conditions at that the SE level of the multilayered WBCA approaches that the two interfaces, the following simultaneous equations are of the square WBCA. Figs. 1(b) and 2(b) show that the obtained: shape of the unit square cells of the WBCAs appears the same when viewed from the front. As the cutoff frequency E +E = E +E (6) i r 1 2 value of the unit square cells is the same for both cases, E E E E i − r = 1 − 2 (7) the side length a of the multilayered WBCA is maintained in η η η η 0 0 the SE equation. Meanwhile, the depth l should be changed E e−γmleff + E eγmleff = E e−jβ0leff (8) effectively. Thus, by introducing the effective length (l ) as 1 2 t eff E E E shown in Fig. 12, the originalSE equation in (3) can be used 1e−γmleff − 2eγmleff = te−jβ0leff (9) η η η for the new multilayered WBCAs. It is noteworthy that l is 0 eff where η represents the impedance of the material-filled alwaysgreaterthanl to providethe same SE level.l can be definedasl =C×l, where C can be derivedfromeffthe full- waveguide and γm is the propagation constant with the eff material-filledwaveguide.Tosolvetheseequations,thereflec- wave simulation, as shown in Table II. First, the SE results tion and transmission coefficients are obtained by using the were obtainedbythe full-wavesimulation ofthe multilayered ratioof E /E and E /E . Thetransmissioncoefficientyields WBCAs withthesamedepth.Afterthoseweresubstitutedfor r i t i (3) to extractthe newl value, the constant value C is defined E 4η η (cid:9) (cid:6)η −η(cid:7)2 (cid:10)−1 as the ratio of the new l value and the physical depth. It is t = 0 1− 0 e−2αmleffe−j2βmleff e−αleff. E (η +η)2 η +η noteworthy that the constant value C convergesto one as the i 0 0 number of layers increases. (10)

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